Graphics controller integrated circuit without memory interface

ABSTRACT

A CMOS integrated circuit that comprises a graphics controller system that consists of a graphics engine and video memory together with some interface blocks, a PCMCIA host adapter, an infrared interface for generating video images on a LCD or CRT display unit, and a video stream interface for receiving video signals. Since the video memory is integrated on the same integrated circuit as the graphics controller, no package pins are required for the memory interface. The pins thus saved are used to provide access to an on-chip PCMCIA host adapter. The internal memory interface is 128 bits wide. Simultaneous performance improvement and power dissipation reduction is achieved because of the wide memory interface and the elimination of the large parasitic capacitances associated with a package pin connection.

This is a Continuation of application Ser. No. 08/262,412 filed Jun. 20, 1994 now abandoned.

BACKGROUND OF THE INVENTION

This invention is related to graphics controller systems and, more particularly, to graphics controller systems with low power dissipation.

As shown in FIG. 1, a typical graphics controller system has a graphics controller integrated circuit 10, which has a graphics engine 12 for manipulating video data, and a CPU interface 13, display interface 14 and video memory interface 15. The graphics controller integrated circuit 10 receives video image data from a CPU (central processing unit) through the CPU interface 13, and after processing the data, stores that information through the video memory interface 15 in a separate video memory 11, also called the video frame buffer. The graphics controller 10 also makes sure that the image data is regularly retrieved from the video memory (through the interface 15) and fed to a display unit through the display interface 14 with a frequency which satisfies the refresh requirements of the display. In some more advanced graphics controller systems, video image data may also be received from other sources, such as a device with a PCMCIA (Personal Computer Memory Card International Association) connector.

The video memory interface 15 of the graphics controller integrated circuit 10 has ports dedicated to interface with the video memory 11. The number of ports required for this interface 15 is the sum of the address, data and control signals required to access the video memory 11. The memory 11 has a size which is a function of the video frame buffer required to support the display resolution. While dynamic random access memory (DRAM) is most commonly used for the video frame buffer, some high performance systems use VRAMs (DRAMs with serial data ports added). A typical VGA (Video Graphics Adapter standard) display in an IBM-compatible mobile computer, often called a notebook computer, with an LCD (liquid crystal display) panel uses a single 256K×16 DRAM integrated circuit as a video frame buffer. A typical SVGA (Super VGA standard) system uses two such DRAMs organized as 256K×32.

Wider data paths between the video memory and the graphics controller allow greater bandwidth for data transfer. However, the wider data paths also increase the pin count of the graphics controller package and the package count of the DRAMs with the accompanying increased manufacturing complexity and costs. A 16-bit data path requires one DRAM package and approximately 30 signal lines to handle the memory address, data, and control signals, while a 32-bit data path requires two DRAM packages and 50 signal lines. Power dissipation is increased as more signal lines are added since each signal line has a parasitic capacitance associated with the package I/O pin, as well as with the conducting trace on the motherboard of the mobile computer system. Therefore, an increase in graphics performance is accompanied by an increase in power dissipation, pin count and package count.

The present invention solves or substantially mitigates these problems with a high performance graphics controller system having low power dissipation, and low pin and package counts.

SUMMARY OF THE INVENTION

According to the invention, there is provided a graphics controller system with increased performance simultaneously with a reduction in power dissipation, point count and package count. Previously external video memory is integrated with the graphics controller system to eliminate the memory interface. The reduction in pin count is used to add the pins associated with a PCMCIA host adapter and thus allow the integration of that function on the same chip, so as to further reduce the package count on the mother board.

The present invention also provides for particular arrangements for logic circuits and output buffer circuits so that large amounts of logic circuitry sufficient to perform graphics controller system functions may be integrated with the large amounts of memory sufficient to act as a high performance video memory. Furthermore, the present invention provides for a wide bus between the integrated video memory and the functional blocks of the graphics controller system. The present invention has circuits in these blocks for manipulating the video data from the wide bus so that data transfer remains compatible to the various operational VGA modes.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 illustrates the general organization of a graphics controller system in the prior art;

FIG. 2 illustrates the general organization of a graphics controller integrated circuit according to the present invention;

FIG. 3A is a circuit diagram of a CMOS logic inverter as connected in a prior art integrated circuit manufactured according to a logic process; FIG. 3B is a circuit diagram of a CMOS logic inverter as connected in a prior art integrated circuit manufactured according to a DRAM process;

FIG. 4 is a circuit diagram of a CMOS logic inverter as connected according to the present invention in an integrated circuit manufactured according to a DRAM process;

FIG. 5 is a cross-sectional diagram of a P-channel transistor in an N-type well, which form most of the analog circuits in the graphics controller portion of the integrated circuit shown in FIG. 2;

FIG. 6A is a circuit diagram of a CMOS driver stage of an output buffer found in the prior art; FIG. 6B is a circuit diagram of a CMOS driver stage of an output buffer according to the present invention;

FIG. 7 is a block diagram detailing the organization of a graphics controller system according to the present invention;

FIG. 8 illustrates the organization of the output signals of the Bus Read Latch of the graphics controller system of FIG. 7; and

FIGS. 9A-9D illustrate the organization of the multiplexer at the output of the Bus Read Latch of the graphics controller system of FIG. 7.

DESCRIPTION OF THE PREFERRED EMBODIMENT(S)

In accordance with the present invention, the graphics controller functions are integrated on the same integrated circuit substrate as the video memory, as shown in FIG. 2. A single integrated circuit 20 has a portion of its substrate for an advanced graphics engine 22, the circuitry which handles the graphics controller functions and manipulates the video data. The integrated circuit 20 also has another portion of the substrate for a video memory 21, in the form of a DRAM. A 128-bit wide data interface 25 connects the graphics engine 22 and the DRAM 21. The DRAM has 7.3 megabits, organized as 56K×128 bits. In every memory cycle, 128 bits are accessed which can then be multiplexed down to the required number of bits for communication to the CPU through a CPU interface 23 or to the display through a display interface 24.

The integrated circuit 20 also has other interfaces, such as an infrared interface 26 for wireless transmission of data between the mobile computer and another device, a PCMCIA host adaptor interface 27 for connections to devices, such as modems, hard disks, etc., which are designed to meet the PCMCIA specification, and a video stream interface 28 for receiving video signals from a variety of sources, such as television or VCR signals. The video stream interface 28 is adapted to the VAFC (VESA Advanced Feature Connector) standards being promulgated by the Video Electronics Standards Association (VESA).

Integrating a large block of DRAM (approximately 7 megabits) on the same substrate with a large block of logic (approximately 40K to 50K of logic gates) required for the graphics engine 22 and various interfaces is not simply a matter of placing DRAM and logic circuits on the same integrated circuit substrate. The optimum technologies for a DRAM and for a logic circuit are electrically incompatible. Hence various steps, described below, must be taken to ensure that the performance of the DRAM circuits and the logic circuits are fully maintained and not compromised.

An integrated circuit process used for building logic gates uses one of the external supply voltages (V_(DD) or V_(SS) depending upon the substrate type) as the voltage to bias the substrate. On the other hand, an integrated circuit process used for building a DRAM uses an internally generated substrate bias voltage which is different from the external supply voltages. This is done primarily to lower the junction capacitance of the memory cell bit lines of the DRAM, as well as to improve the memory cell refresh time.

For example, in commonly used CMOS technology today, the substrate material is P-type silicon. A logic process uses the externally supplied V_(SS), or ground, voltage to connect to the substrate. The V_(SS) line is also used in the circuit areas to provide the ground path for current flow in the pulldown, N-channel transistors in the logic circuits. FIG. 3A illustrates this point with a representative logic gate, an inverter having a pull-down, N-channel transistor 31 and a pull-up, P-channel transistor 32. The PMOS transistor 32 has its source connected to a metal line 42 at the positive supply voltage, V_(DD), and the NMOS transistor 31 has its source connected to a metal line 41 at V_(SS). The P-type substrate in which the NMOS transistor is placed is also connected to the V_(SS) line 41. In FIG. 3A (and 3B and 4), node 30 represents a metal-to-N+ source contact and node 40 represents a metal-to-P+ substrate contact.

Thus the same V_(SS) metal tracks in the logic integrated circuit serves two functions: 1) as a substrate tap every 25-50 microns across the substrate surface, and 2) as a source terminal of the N-channel transistors of the logic circuits. The substrate taps are necessary to protect the circuits from going into a latch-up condition during operation, since each logic gate has both N-type and P-type transistors.

In a CMOS DRAM, however, the typical DRAM array is built with only N-type transistors and capacitors, and a major goal is to minimize the parasitic capacitance of the memory bit line. Since the N-type bit line junction areas contribute to a majority of the bit line capacitance and since the junction capacitance is greatly reduced by a reverse junction bias voltage, the P-type substrate is typically biased at -1.5 volts, termed V_(BB). This voltage is generated from an on-chip charge pump and thus has a limited capacity and a high output impedance. This results in the substrate voltage being relatively "noisy" due to the precharging and discharging of the large junction areas associated with the memory array, that are capacitively coupled to the substrate.

In the DRAM, the small amount of on-chip logic which handles the memory address decoding and the data read and write functions typically uses the V_(SS) metal tracks only to connect to the source terminal of the N-channel, pulldown transistors and not as a substrate tap. As shown by a representative logic gate, an inverter, in FIG. 3B, a pull-down, N-channel transistor 33 has its source connected to a V_(SS) metal line 43. The P-type substrate of the NMOS transistor 33 is at V_(BB).

In fact, DRAMs typically do not have any substrate taps in the middle of the circuitry. The substrate taps are only made at the edges of the die. Since most of the logic blocks in a DRAM consist of a few cells, repeated many times, which together form a small portion of the total chip area, large P-to-N diffusion spacings, typically 25 microns, can be maintained in the logic cells to avoid latch-up. In contrast, in a logic circuit, which has many different cell types connected in a relatively random manner, the cell size is very important as it determines the total chip area. The P-to-N diffusion spacings are minimized, typically 5 microns, which requires the use of substrate taps in every cell to avoid latch-up.

To combine a significant amount of random logic to a significant amount of DRAM in a single integrated circuit requires that this problem be overcome. The present invention combines the random logic, the graphics engine 12 and interfaces, with the DRAM 11, in an integrated circuit 20 manufactured in accordance with a DRAM process. The logic circuits of the integrated circuit are redesigned to decouple the V_(SS) line connected to the source terminals of the N-channel, pulldown transistors from the P-substrate tap. As shown in FIG. 4, the source of the N-channel, pulldown transistor 35 of a representational logic circuit is connected to a V_(SS) line 45 (at 0 volts), while the substrate is tapped by a V_(BB) line 47 (at -1.5 volts). The P-to-N diffusion spacings are then minimized without deleterious consequences.

Additionally, the graphics engine 22 of the integrated circuit 20 has analog circuits. In an exemplary analog circuit, a low-pass filter is often used and an RC circuit is required. Heretofore, the capacitor of the RC circuit has been typically formed by an NMOS transistor with its gate forming one terminal and the shorted source/drains forming the other terminal of the capacitor. Since the body bias of this transistor is the noisy substrate voltage generated from the on-chip charge pump required for the DRAM 21, some of the noise couples inevitably into the low-pass filter circuit. To avoid this problem, the analog circuits according to the present invention are designed with mostly P-channel transistors within independent N-wells which are connected to the positive and relatively quiet reference voltage, V_(DD), as shown in FIG. 5. The N-wells isolate the terminals 37 and 38 of the capacitors and the rest of the analog circuits from the "noisy" substrate voltage.

On the periphery of the integrated circuit are buffer circuits for transferring signals to and from the external world. Problems arise with the DRAM technology in the driver stage circuit of each output buffer. Shown in FIG. 6A is a representative output driver stage found in the prior art. Basically an inverter, the driver stage has two transistors, an N-channel, pulldown, driver transistor 50 having its source connected to a voltage supply bus 52 at an external negative supply voltage, V_(SSQ), and a P-channel, pullup, driver transistor 51 having its source connected to a voltage supply bus 53 at an external positive supply voltage, V_(DDQ). The words, "negative" and "positive," refer to one supply voltage relative to the other supply voltage and the "Q" in the subscript indicates that the supply voltages are not necessarily the same as the supply voltages, V_(DD) and V_(SS), in the other parts of the integrated circuit. This allows the interior portions of the integrated circuit to operate at voltage levels, 0-+3.3V, while the peripheral output driver circuits operate at different levels, 0-+5.0V, for example. Furthermore, the separation of supply voltages provides for some insulation from noise between the interior and peripheral portions of the integrated circuit. The drains of the two transistors 50 and 51 are connected together and to an output terminal 54. The gates of the transistors 50 and 51 are also connected together to an input terminal 57 connected to the rest of the buffer circuit (not shown).

During the switching of output signals, the output signal voltages invariably tend to overshoot the V_(DDQ) and V_(SSQ) supply voltages due to an impedance mismatch between the driver transistors and the external load. When the output signal voltage, DATA OUT, is being driven high in response to an internal signal, dataout*, going low at the input terminal 57, for instance, the prior art design results in a parasitic diode 55, marked by dotted lines, becoming forward-biased when the overshoot exceeds 0.6 volts. The diode 55 is formed by the junction of the drain of the P-channel, pullup transistor 50 and the N-well holding the transistor, which is also connected to V_(DDQ). This forward-biasing action results in the injection of positive charges, or holes, into the substrate which works against the on-chip substrate bias voltage generator. The amount of hole injection is a function of the severity of the overshoot, the number of output buffers, and the frequency of switching. If the substrate bias voltage generator is overwhelmed by excessive hole injection, functional failures or soft errors occur in the on-chip DRAM.

To avoid this problem, a new output driver circuit, shown in FIG. 6B, is used. In the drawing, the same reference numerals are used where the operation or connection of the referenced element remains unchanged from FIG. 6A. Different reference numerals are used if the operation or connection of the element is different. In the new, representative driver circuit, for each bank of buffer circuits at particular V_(DDQ) and V_(SSQ) voltages, the N-wells in which the P-channel driver transistors 51 of the bank are located are raised to a voltage higher than the V_(DDQ) voltage for the bank. An on-chip bias generator is connected to the V_(DDQ) bus 53 for a reference to generate a voltage at NV_(DD), 1 volt higher than V_(DDQ). The bias generator (not shown) is connected to a bus 59 at NV_(DD), which is connected to the N-wells of each of the P-channel transistors 51. If several P-channel transistors 51 are in a single N-well, the bus 59 is connected to the N-well in a series of taps, one located near each transistor 51. This arrangement lowers the possibility of latch-up.

For each bank of output buffers on the same integrated circuit, a different NV_(DD) bias generator, referencing the V_(DDQ) supply for that bank, is used to generate the higher voltage. This allows the N-well(s) of an output buffer bank which is driven from a +3.3V supply to be biased at +4.3V, while an output buffer bank driven by a +5.0V supply, has its N-well(s) biased at +6.0V.

As shown in FIG. 6B, the parasitic diode 58 formed by the drain of the transistor 51 and the N-well holding the transistor 51 now has an extra 1 volt of N-well bias. The diode 58 does not become forward-biased unless the overshoot exceeds 1.6V. This extra margin of safety results in a greatly diminished level of hole injection into the substrate and thus prevents the occurrence of soft errors or functional failures in the on-chip DRAM.

Integrating the video memory, the DRAM 21, with a graphics controller results in significant power savings compared to present graphics controller systems with external DRAM. Capacitance in present graphics controller systems is comprised of the capacitance of the I/O pins of the DRAM packages and the controller package plus capacitance of the traces on the motherboard which carries and connects the DRAM and controller packages. The present invention has a roughly twenty-fold reduction of the video memory address, data and control bus capacitance. This results in an equivalent power savings since most of these lines are continuously switching at high frequencies.

Another source of power savings is the 128-bit wide memory word which can be transferred between the graphics engine 22 and the video memory 21. The controller, i.e., the graphics engine 22, has 128 bits of data available after one DRAM read cycle. In comparison, the graphics controller system in the prior art requires four or eight read cycles, depending upon a 32-bit or 16-bit wide DRAM organization, respectively. Since a fixed amount of power is consumed every DRAM cycle, the present invention has a savings of three-fourths to seven-eighths of the prior art power dissipation.

Furthermore, the present invention uses memory very efficiently. The capacity of the video memory 21 is not required to fall on high order binary boundaries, such as combinations of DRAM integrated circuits forming a memory of 32K×128 bits, or 64K×128 bits, the next larger size. In the present invention, the addition of memory blocks, with a typical size of 256K(2¹⁸) bits each, achieves the required capacity for the video memory 11. Memory capacity can be customized for a particular application. For example, a 1024×768×8 display requirement requires a video memory of 6.4 megabits, which can be built with 24 memory blocks. With external DRAMs, a video memory of 8 megabits is required since the standard DRAM package has 4 megabits. The video memory 21 of the integrated circuit 20 can be organized to be of any width, depth or capacity and need not follow the multiplexed addressing architecture associated with standard DRAMs.

With the ability to incorporate large amounts of logic and memory in a single integrated circuit, the present invention provides for a video memory and logic for graphics control operations in one integrated circuit. FIG. 7 illustrates the organization of the advanced graphics controller system of FIG. 2 in greater detail. As stated previously, the memory 21 is organized from dynamic RAM memory cells arranged 56K×128 bits wide. Stated differently in terms of memory blocks, the memory 21 has the storage capacity of 2¹⁸ ×28 bits. The 128-bit interface 25 in FIG. 2 is realized by a 128-bit wide bus 61, organized as sixteen 8-bit bytes, so that a Write operation can be performed at the byte level into the memory 21. Connected to the bus 61 is a Graphics User Interface (GUI) Acceleration block 62, part of the Graphics Engine 22 of FIG. 2. The CPU Interface 23 of FIG. 2 is realized by a Host Bus Interface block 63 in FIG. 7, and the Display Interface 24 is by a CRT Display block 64 and an LCD Display Interface block 65. All the blocks 62-65 are indicated by dotted lines in FIG. 7. Not shown in FIG. 7 are the Infrared Interface 26, PCMCIA Host Adaptor 27 and the Video Source Interface 28. The circuits for the Interfaces 26 and 28, and Adaptor 27 are presently found in separate printed circuit boards in personal computer systems and may be integrated onto the single integrated circuit with the techniques described previously.

The GUI acceleration block 62 has a 128-bit wide register 70, which receives data from the bus 61. The register 70 splits its contents into two parts, 64-bits apiece, to a 64-bit BIT BLock Transfer (BITBLT) operation unit 71 for performing the operations. The output of the unit 71 is fed into an assemble register 72 on a 64-bit wide path. After a BITBLT operation, the register 72 builds up a 128-bit word for transfer back to the bus 61. This organization represents the best compromise between performance and space on the integrated circuit; the transfer rate is maximized between the memory 21 and the operation unit 71, yet an optimum size of 64 bits for the unit 71 is maintained. A 128-bit BITBLT operation unit occupies a very large amount of integrated circuit space, while a unit for 32 bits slows BITBLT operations too much.

The host bus interface block 63 lies between the bus of the host, i.e., the CPU of the computer system, and the bus 61. The interface block 63 provides a bidirectional data path between the 128-bit bus 61 and a 32-bit bus of the host. The block 63 has a Bus Read Latch 73 which holds a 128-bit wide word from the bus 61. The output of the latch 73 is connected to the input of a multiplexer 74, which selects 32 bits from the 128-bit latch 73 for the host bus. For host Read operations, the selected 32 bits should contain four consecutive bytes in the host bus address space. Depending upon the VGA-compatible format and other extended storage formats in use, these four bytes may be scattered among the 16 bytes, 16×8 bits equals 128 bits, of data stored in the latch 73.

The output of the latch 73 is illustrated in FIG. 8 with each of the bytes labeled 0-F. To implement 4-byte access properly for all VGA-compatible and additional extended storage formats, the multiplexer 74 is implemented as four separate single byte multiplexers 74A-74D, one for each byte read back upon the host bus. Each of the 8-to-1 multiplexers 74A-74D are illustrated in FIGS. 9A-9D respectively together with the particular input bytes from the latch 73. Each of the multiplexers 74A-74D respectively generates bytes 0-3 for the host bus.

The logic to generate the control signals, selda(2:0), seldb(2:0), seldc(2:0), and seldc(2:0), for the multiplexers 74A-74D is listed in VHDL code in Appendices 1 and 2A-2D. These control signals are derived from VGA standard control bits in programmable control registers which determine the storage format in use, and additional internal state information in the memory controller state machine. The present invention uses the following standard control bits:

SR4 3!=Chain-4

GR5 3!=Read Mode

GR5 4!=Odd/Even

GR4 0!=Read Map Select 0!

GR4 1!=Read Map Select 1!

GR6 0!=APA/Text*, Graphics Mode

and an extended mode control bit:

PACPIX=Packed Pixel Format

As indicated in Appendix 1, these control bits are used to generate control signals, tmp₋₋ pack, pack, rdplanar and wrplanar, which are used ultimately in generating the selda(2:0), seldb(2:0), seldc(2:0), and seldc(2:0) control signals. From these control signals, other control signals are generated for each of the multiplexers 74A-74D. For example, the control logic and signals for the first multiplexer 74A are illustrated in FIG. 2A. The control signals in Appendix 1 generate control signals sela(0)-sela(7). These eight control signals then generate the three selda control signals. The end of Appendix 2A shows how the multiplexer 74A responds to the control signals by selecting one of input eight bytes, mrd₋₋ dta(X DOWNTO Y), as the output byte, cpu10.

Appendices 2B-2D similarly illustrate the details of the control signals and operation of the multiplexers 74B-74D respectively.

With reference to FIG. 7 once again, the block 63 also has a FIFO (First-In, First Out) register 77 which has its input terminals connected to the 32-bit host bus for transfer of data from the host bus. The output terminals of the FIFO 77, also 32 bits wide, are connected to a graphics controller unit 76, which also has its input terminals connected to the output terminals of the multiplexer 74. The graphics controller unit 76 manipulates data bits and can selectively load a single, or multiple, byte to the bus 61 through four drivers 75 in response to commands from the CPU (not shown). For VGA compatibility, the 32 bits sent from the Bus Read Latch 73 to the graphics controller unit 76 during a memory write operation are always be the four bytes from the four VGA planes containing the last byte read from the memory module 60 on the host bus. The multiplexer 74 is set properly in a VGA compatible mode upon completion of each Read operation. This setting for the multiplexer 74 is again dependent upon VGA or extended mode and is derived from logic equations similar to those shown in appendices 1 and 2A-2D. The four drivers 75 reverse the data selection operation performed by the multiplexer 74. The multiplexer 74 selects four bytes out of the 16 bytes read from the memory 60 to forward to the host bus. The drivers 75 position the four bytes from the host bus in a write operation properly in the 16 byte slots on the memory bus 61 so that the data is stored properly for subsequent retrieval. Control of these drivers 75 is derived from the memory controller control states and control register bits that define the VGA-compatible storage format, or other additional extended storage format, in use.

The CRT display block 64 provides a data path between the memory 21 and the CRT display which is compatible with the VGA standard. The block 64 has a Data Rotate unit 80, which receives 128 bits from the bus 61. The unit 80 is connected over four 32-bit paths to the input terminals of a CRT FIFO register 81 which has a capacity of 4 words, each word 128 bits wide. Stated differently, the FIFO register 81 is 128 bits wide and four stages deep, and can be filled in four memory fetches. The output terminals of the FIFO register 81 are connected to a VGA Display Path unit 82 over a 32-bit wide path. All VGA compatible graphics controllers for notebook computers today are based on a 16-bit or 32-bit memory bus to an external video memory buffer. The present 128-bit bus architecture, in comparison, allows improved performance while reducing power consumption. However, to achieve VGA compatibility and improve performance, byte swapping is required in transferring data from the memory bus 61 to the FIFO register 81. This swapping is implemented in the Data Rotate unit 80. From the 128 bits of the FIFO register 81, 32 bits are selected and sent to the VGA Display Path unit 82. Appendix 3 specifies the control signals and implementation in terms of the control register bits which define the VGA storage format or extended mode storage format in use, as well as the memory controller control states.

The control signals are:

fontcy is a signal derived from the internal state machine and indirectly from the previously identified control signal, GR6 0!; a control signal, such as fontcy, is found in present VGA compatible controllers to determine a font or ASCII fetch operation in text mode.

swap 0, swap 1 are the 0 and 1-order bits of the CRT address counters found in VGA compatible controllers; these signals are derived from the Chain-4 and Odd/Even control signals mentioned previously.

rscntb0, rscntb1 are the 0 and 1-order bits of the 5-bit row scan counter found in VGA compatible controllers; the row scan counter is used for tracking the rows of a character in text mode.

1word is the Chain-4, or SR4 3!, control signal identified previously.

crsr₋₋ dtct is the cursor detect signal in VGA-compatible controllers; and

TEXT, apa are the true and inverted of the GR6 0! control signal previously identified. These control signals are used to generate further signals, memol₁₃ dta and memc2₋₋ dta. Stated generally, these two signals are either the crsr₋₋ dtct signal in text mode, or bit 96 (or bit 36 respectively) of the data bits from the 128-bit word on the bus 61 in graphics mode. The signals, mema₋₋ dta, are basically the four 32-bit words of data formed from the 128-bit word on the bus 61. The words for the bit locations, 127-96 and 63-32, are modified so that the bits 96 and 32 are either crsr₋₋ dtct in text mode or respectively data bits 96 and 32 from the bus 61. Finally, swapa and swapb are the control signals to the multiplexers in the Data Rotate unit 80. It should be noted that the symbol, "&", represents a concatenation of signals.

Appendix 4 illustrates the operation of the Data Rotate unit 80, which receives the mema₋₋ dta signals as input and transmits crt₋₋ fin signals as output to the FIFO register 81. The first VGA (32-bit) word, crt₋₋ fin(31 DOWNTO 0), may be filled by any one of the four incoming 32-bit words from the bus 61, depending upon the state of control signals swapa. Similarly, the third VGA (32-bit) word, crt₋₋ fin(95 DOWNTO 64), may be filled by any one of the four ithe bug 32-bit words from the bus 61, depending upon the state of control signals swapb. The second and fourth VGA words, crt₋₋ fin(63 DOWNTO 32) and crt₋₋ fin(127 DOWNTO 96), are respectively filled by the third and first incoming 32-bit words from the bus 61.

The CRT FIFO 81 then selectively feeds 32-bit words into a VGA Display Path unit 82 and a Color Palette RAM 83. The RAM 83 is, in turn, connected to a digital-to-analog converter (DAC) 84. The RAM 83 feeds 18 bits of data, 6 bits for each component color, to the DAC 84. The DAC 84 generates the analog signals for a CRT color display.

The RAM 83 also feeds data into the LCD Display Interface block 65 which is organized for dual scan LCD panel displays. The general operation of the block 65 is that a Shader unit 96 receives the data from the RAM 83. The unit 96 generates the grayscale values for the LCD pixels. In passing, it should be noted that the word, grayscale, implies intensity for a color LCD display. These values are sent to a Formatter unit 92 which, as the name implies, formats the grayscale values for the integrated circuit(s) which drive the electrodes of the LCD display. The Shader unit 96 also sends its grayscale values through several buffer units 95, 94, 93, 90 and 91 (and along the bus 61) before being formatted and transmitted by the Formatter unit 92 for a dual scan operation. Dual scan LCD panels are commonly used today in notebook computers and the buffer units of the block 65 provide for the memory by which, in alternating operation, the display in one LCD panel is updated by the Shader unit 96 while the display in the second panel is maintained from memory.

Therefore, while the description above provides a full and complete disclosure of the preferred embodiments of the present invention, various modifications, alternate constructions and equivalents may be employed without departing from the true scope and spirit of the invention. For example, while the present invention has been described in terms of an integrated circuit with a memory capacity of some 7.3 megabits and some 40-50K logic gates, one could use the present invention to build an integrated circuit of reduced size. An integrated circuit having a memory capacity of 2 megabits, the capacity of basic VGA video memory in graphics cards, with 30K logic gates, the approximate amount of logic in present graphics controller integrated circuits, still realizes the advantages of the present invention. Costs, power dissipation and occupied space are reduced, and performance is enhanced, for instance. The present invention, therefore, should be limited only by the metes and bounds of the appended claims. 

What is claimed is:
 1. An integrated circuit comprisinga logic portion having at least 30K logic gates, said logic gates having first dopant-type and second dopant-type MOS transistors, said first dopant-type MOS transistors having sources connected to a first voltage supply line, said second dopant-type MOS transistors having sources connected to a second voltage supply line, and said second dopant-type MOS transistors placed in a substrate region connected to third voltage supply line, said third voltage supply different than said second voltage supply; and a memory portion interconnected with said logic portion, said memory portion having a capacity of at least 2 megabits.
 2. The integrated circuit of claim 1 wherein said substrate region is connected to said third voltage supply line by taps.
 3. The integrated circuit of claim 1 wherein said first dopant-type MOS transistors comprise PMOS transistors, said second dopant-type MOS transistors comprise NMOS transistors, and said third voltage supply is lower than said second voltage supply.
 4. An integrated circuit comprisinga logic portion having at least 40K logic gates, said logic gates having first dopant-type and second dopant-type MOS transistors, said first dopant-type MOS transistors having sources connected to a first voltage supply line, said second dopant-type MOS transistors having sources connected to a second voltage supply line, and said second dopant-type MOS transistors placed in a substrate region connected to a third voltage supply line, said third voltage supply different than said second voltage supply; and a memory portion interconnected with said logic portion, said memory portion having a capacity of at least 7.3 megabits.
 5. The integrated circuit of claim 4, wherein said substrate region is connected to said third voltage supply line by taps.
 6. The integrated circuit of claim 4, wherein said first dopant-type MOS transistors comprise PMOS transistors, said second dopant-type MOS transistors comprise NMOS transistors, and said third voltage supply is lower than said second voltage supply.
 7. In an integrated circuit having a logic portion having at least 30K logic gates and a memory portion coupled to said logic portion, said memory portion having a capacity of at least 2 megabits, a capacitor comprisinga first dopant-type transistor in an a second dopant-type well in a first dopant-type semiconductor substrate, said first dopant-type transistor having a gate, first and second source/drains, said first source/drain connected in common to said second source/drain to form a first terminal of said capacitor, said gate forming a second terminal of said capacitor, said a second dopant-type well connected to a first power supply, and said substrate connected to a second power supply at a negative voltage with respect to said first power supply; whereby said capacitor is isolated from electrical noise in said substrate.
 8. The capacitor of claim 7, wherein said second power supply is generated from a substrate bias generator.
 9. The capacitor of claim 7, wherein said first dopant-type transistor comprises a PMOS transistor, said second dopant-type well comprises an N-well, and said first dopant-type semiconductor substrate comprises a P-type substrate.
 10. The capacitor of claim 9, wherein said second power supply is generated from a substrate bias generator.
 11. The capacitor of claim 10, wherein said second power supply is at approximately -1.5 volts.
 12. The capacitor of claim 10, wherein said first power supply is at approximately +3.3 volts.
 13. The capacitor of claim 7, wherein said logic portion has at least 40K logic gates; and said memory portion has a capacity of at least 7.3 megabits.
 14. The capacitor of claim 13, wherein said second power supply is generated from a substrate bias generator.
 15. The capacitor of claim 14, wherein said second power supply is at approximately -1.5 volts.
 16. The capacitor of claim 14, wherein said first power supply is at approximately +3.3 volts.
 17. The capacitor of claim 14, wherein said first dopant-type transistor comprises a PMOS transistor, said second dopant-type well comprises an N-well, and said first dopant-type semiconductor substrate comprises a P-type substrate.
 18. An integrated circuit comprisinga logic portion having at least 30K logic gates; a memory portion coupled to said logic portion, said memory portion having a capacity of at least 2 megabits, and an analog circuit having a capacitor, said capacitor comprising a first dopant-type transistor in a second dopant-type well in a first dopant-type semiconductor substrate, said first dopant-type transistor having a gate, first and second source/drains, said first source/drain connected in common to said second source/drain to form a first terminal of said capacitor, said gate forming a second terminal of said capacitor, said second dopant-type well connected to a first power supply, and said substrate connected to a second power supply at a negative voltage with respect to said first power supply; whereby said capacitor is isolated from electrical noise in said substrate.
 19. The integrated circuit of claim 18 wherein said second power supply is generated from a substrate bias generator.
 20. The integrated circuit of claim 18, wherein said first dopant-type transistor comprises a PMOS transistor, said second dopant-type well comprises an N-well, and said first dopant-type semiconductor substrate comprises a P-type substrate.
 21. The integrated circuit of claim 20 wherein said second power supply is generated from a substrate bias generator.
 22. The integrated circuit of claim 21, wherein said second power supply is at approximately -1.5 volts.
 23. The integrated circuit of claim 21, wherein said first power supply is at approximately +3.3 volts.
 24. The integrated circuit of claim 18, wherein said logic portion has at least 40K logic gates; and said memory portions has a capacity of at least 7.3 megabits.
 25. The integrated circuit of claim 24 wherein said second power supply is generated from a substrate bias generator.
 26. The integrated circuit of claim 24 wherein said first dopant-type transistor comprises a PMOS transistor, said second dopant-type well comprises an N-well, and said first dopant-type semiconductor substrate comprises a P-type substrate.
 27. The integrated circuit of claim 26 wherein said second power supply is generated from a substrate bias generator.
 28. The integrated circuit of claim 27, wherein said second power supply is at approximately -1.5 volts.
 29. The integrated circuit of claim 27, wherein said first power supply is at approximately +3.3 volts. 